The DC current source uncertainty components listed in Table 2 to Table 5 include both those derived from Eq. 1 and additional systematic components (voltmeter calibration, reproducibility, long-term drift, and loop gain). Each component is explained below. Feedback resistance is the combined standard uncertainty from the QED calibration report, i.e., one half of the expanded uncertainty (k = 2), see Table 1. This is only a relative component (Table 3 and Table 5), there is no absolute uncertainty component (Table 2 and Table 4) for the feedback resistance. Measurement noise is the average “noise” of multiple samples. In Table 2 and Table 4 the measurement noise is defined by the standard deviation of the offset (I = 0) measurement. In …show more content…
2 is shown in Table 6 (absolute term) and Table 7 (relative term). These tables vary by DUT model. For efficiency, the values in the table are determined after evaluating several DUTs of the same model and used for subsequent DUTs of this model if the measurement noise is less than the values in the tables. A similar set of tables is generated for the Keithley 6430 current source (not presented). Table 6. Absolute term for the standard uncertainty budget of the current-to-voltage conversion gain (G(I)) of a DUT using the Keithley 263 DC current source. Absolute standard uncertainty [V x 10-6] Uncertainty components Type Range 1x104 V/A 1x105 V/A 1x106 V/A 1x107 V/A 1x108 V/A 1x109 V/A Current B 7.18 26.3 30.4 26.9 43.6 40.9 Measurement noise A 11.2 22.6 32.7 25.9 41.2 32.4 Voltage measurement B 0.14 0.14 0.14 0.14 0.14 0.14 Reproducibility (6 months) A 0.00 0.00 0.00 0.00 0.00 0.00 Loop gain B 0.00 0.00 0.00 0.00 0.00 0.00 Combined absolute standard uncertainty term of G(I) measurement 13.3 34.7 44.6 37.4 60.0 52.2 Table 7. Relative term for the standard uncertainty budget of the current-to-voltage conversion gain (G(I)) of a DUT using the Keithley 263 DC current source. Relative standard uncertainty [x10-6] Uncertainty components Type Range 1x104 V/A 1x105 V/A 1x106 V/A 1x107 V/A 1x108 V/A 1x109 V/A Current B 3.18 5.81 5.61 6.46 8.57 14.6 Measurement noise A 0.19
CP3208 devices are successive approximation 12-bit ADC with on-board sample and hold circuitry. The MCP3204/3208 devices operate over a broad voltage range (2.7 V - 5.5 V). Low current design permits operation with typical standby and active currents of only 500 nA and 320 μA, respectively. Fig.3 shows the functional block diagram of MCP3208 ADC. Fig.3 Functional Block Diagram of MCP3208 ADC
are more uncertain than the others? How could uncertainty be worked into the analysis? Is
equation to loop 1 of Fig. 2 and current balance equation to node 1, the state space equations (1) and (2)
In order to calculate the PSRR of the LDO, sine wave with 100mv amplitude is added to power supply to simulate noise of power supply. The PSRR of the proposed LDO is analyzed in the range of 10KHz to 10MHz and the simulation results are shown in Fig. 14. As it is shown, LDO works properly from 10KHz to 2.4MHz because after that Vout amplitude will become more than 10mV , so it cannot be neglected in compare with input sine wave which is 100mV. The proposed excessive current extraction (ECE) technique results in high frequency PSR of -88.69dB at 1MHz frequency. So, we can see the improvement of -48 dB and -13.69dB at 1MHz in compare with cap-less LDO without and with PSRR enhancer, respectively [14]. The LDO was
The comparison of above three algorithms for 8, 16 and 32 bit operands with corresponding voltage and frequency are tabulated in table I
The average deviation describes the precision of the results. It was determined the results our group obtained for were very precise. This is because our average deviation for Keq was only 6.8 which comes out to be a 6. percent error. Due to our deviation being so low it indicates that the equilibrium constant is indeed a “constant”.
2.8 CA3130 Op-Amp CA3130A and CA3130 are op-amp that combine the advantage of both CMOS and bipolar transistors. Gate-protected P-channel MOSFET transistor are used in the input circuit to provide very high-input impedance, very low input current and exceptional speed performance. The use of P,OS transistor in the input stage results in common mode input voltage capability down to 0.5V below the negative supply terminal, an important attribute in single-supply application. The CA3130 series circuit operates at supply voltage ranging from 5V to 16V.
One of the most common ways to parametrize a circuit is by using the equivalent model of the transistor to the small signal analysis (used for low frequencies), or the S-parameters analysis, especially for RF circuits. However, these tests are only accurate enough for sizing linear devices, which is not the case of power amplifiers. Thus, it is necessary to resort to the analysis of large signals. For large signals, both the output and input impedances have to consider the values of frequency, DC voltage, output power, temperature, input power and
The variables been shown in the simulater are the voltage, current, and ressistance. V(volts) = I(Ampers)* R(Ohms).
One more important parameter is the Noise figure (NF), it is defined as a degradation of the signal to noise ratio as it passes through a device, for example, a spectrum analyzer. It could be defined with the Noise Factor (F) which is given as:
During lab, we have designed circuits proving each of these electrical principles. Now, let's apply this knowledge to a real world application.
Figure.10 (a) Hardware test bench set up (b) Gating pulses for 70 KHz from DSP processor (c) Input voltage and input current waveforms for 230Vrms (d) Input voltage and input current waveforms for 110 Vrms
In many methods, skin and proximity effects are very important. Another important parameter is alternative current (a.c.) resistance, rac. This parameter is frequency dependence. It can be shown that rac increased with the increased of frequency (Du, & Burnett, (2000), (Demoulias, Labridis, Dokopoulos & Gouramanis, 2007), (Desmet, Vanalme, Belmans, & Van Dommelen, 2008). Some research papers used value from published graph such as by The Okonite Company and Anixter Inc. (The Okonite Company, 2001), (Anixter Inc., n.d.). However upon inspection, it was found that the graph is produced on the basis of fundamental frequency of 60 Hz and using imperial unit. Some other sources, although on 50 Hz as fundamental basis, give limited data such as (Moore, 1997), (Coates, n.d). As an alternative, formula from IEC 287-1-1 was used to calculate the rac (IEC, 1994).
Extended range of 120dB utilizing the linear to logarithmic transformation of photocurrent in to sense signal voltage with compromise on contrast and brightness [124].
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